• 专利附录
  • 专利说明
  • 权利要求
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  • 同族专利
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    • 专利摘要:
    Provided is a receiver and an FBMC reception method for reducing the decoding latency and increasing the data rate in a communication system using a handshake exchange protocol or an access protocol TDMA. The receiver introduces zero stuffing values in place of the last samples of the last block of samples of a FBMC packet, without waiting for the end of this packet. The decoding of the FBMC packet is thus decoded more rapidly, without significant degradation of the error rate and without decreasing the out-of-band rejection rate of the FBMC signal.
    公开号:FR3034936A1
    申请号:FR1553123
    申请日:2015-04-10
    公开日:2016-10-14
    发明作者:Jean-Baptiste Dore
    申请人:Commissariat a lEnergie Atomique CEA；Commissariat a lEnergie Atomique et aux Energies Alternatives CEA；
    IPC主号:
    专利说明:

    [0001] TECHNICAL FIELD The present invention generally relates to the field of telecommunication systems using a multi-carrier filterbank modulation, also called Filter Bank Multi-Carrier (FBMC) systems. . STATE OF THE PRIOR ART Telecommunication systems using a multi-carrier modulation are well known in the state of the art. The principle of such modulation is to divide the transmission band into a plurality of sub-channels associated with subcarriers and to modulate each of these subcarriers with the data to be transmitted. The most widespread multi-carrier modulation is undoubtedly Orthogonal Frequency Division Multiplexing (OFDM) modulation. This is implemented in wireless local area networks WLAN, WiFi, high speed wireless internet access (WiMAX), digital broadcasting systems (DVB-T, ISDB-T, DAB), asymmetric digital links (xDSL), the fourth generation of cellular telephony (LTE), etc. The spectral occupation of an OFDM signal, however, is substantially greater than the band of subcarriers it uses. Indeed, the temporal location 25 of the signal being very good (the signal is delimited by a time slot), the frequency localization is not (secondary lobes in cardinal sine spreading out of the band). OFDM modulation is therefore not an optimal solution for applications requiring high out-of-band rejection rates. FBMC (Filter Bank Multi Carrier) can be used as an alternative to OFDM. The principle of FBMC modulation is based on a filter bank synthesis on transmission and a filter bank analysis on reception. The filters used consist of frequency-shifted versions of a low-pass prototype filter satisfying the Nyquist criterion. A detailed description of the FBMC modulation can be found in the article by B. Hirosaki entitled "An orthogonally multiplexed QAM system using the discrete Fourier transform" published in IEEE Trans on Comm., Vol.
    [0002] 29 No. 7, pp. 982-989, July 1981, as well as in the article by P. Siohan et al. entitled "Analysis and Design of OFDM / OQAM based on filterbank theory" published in IEEE Trans .on Signal Processing, Vol 50, No 5, pp. 1170-1183, May 2002. In the frequency domain, a FBMC signal can be represented by the response of the synthesis filter bank, namely the response of the prototype filter, translated at the different frequencies of the subcarriers, the out-band spreading does not exceed twice the frequency difference between sub-carriers In other words, it is enough to use an unmodulated subcarrier to isolate two independent groups of subcarriers, this good frequency localization of the signal is paid correlatively by a time spread of the FBMC symbols. of a large number of FBMC symbols, the time spread is negligible with respect to the duration of the packet On the other hand, when the FBMC symbol packets are small, especially when the payload the signal is weak compared to that of the preamble, the time spread can become very penalizing in terms of flow. This situation occurs in the case of a so-called handshake protocol between a transmitter (eg a source terminal) and a receiver (eg a destination terminal). This communication protocol is illustrated in FIG. 1. The FBMC symbol packet is transmitted by the source during a time interval T data "This duration includes a setup time 1, a duration NT corresponding to the Ars symbols to be transmitted, where T is the duration of a symbol as well as a decay time equal to 1. Time 2 can be shown to be (K -11 2) T (in the case of 0QAM modulation) where K is the overlap factor (overlapping factor), that is to say the number of successive FBMC symbols overlapping in time.
    [0003] Thus, if we note the moment of emission of the last FBMC symbol of the packet, this packet will be temporally spread until tempstend + r ". In addition, if we note 0- the propagation time of the signal between the source terminal and the destination terminal, the decoding of the packet ends at the earliest instant at the time ± 2+ (Y After decoding the packet, the destination terminal transmits an acknowledgment message to the source terminal.
    [0004] In the same way as above, the source terminal can only recognize the acknowledgment at time teancdk + r + ci where telk is the end of the acknowledgment message. It is thus understood that the transmission of a data packet according to this protocol is penalized by a latency time 2r, due to the time spreading of the FBMC signal.
    [0005] Another situation in which the time spread of the FBMC symbols penalizes the data rate relates to the use of a TDMA (Time Division Multiple Access) communication protocol. According to this protocol, the access to the common transmission resource (here all the N subchannels) is divided into transmission time slots allowing different users to transmit their data packets during the intervals that have been respectively allocated. When the different users transmit their packets by means of FBMC modulation, the temporal occupation of the transmission intervals is not optimal. Indeed, the rise and fall times of the OFDM signal lead to a temporal occupancy rate of the transmission intervals of the order of (Ttdma 2r) I Ttdma where Ttdire is the duration of a transmission interval, as represented in the timing diagram (a) of FIG. 2. In order to reduce the temporal occupancy of the transmission slots, it is possible to reduce the size of these slots at the cost of a temporal overlap of the successive FBMC packets and thus of an increase in the interference level, as illustrated in the chronogram (b) of the 3034936 4 Fig. 2. In order to reduce the time spread of a packet of FBMC symbols, it has been proposed in Bellanger's article entitled "Efficiency of filter bank multicarrier techniques 5 in burst radio transmission" published in IEEE. Proc. of Global Telecommunications Conference (GLOBECOM 2010), pp. 1-4, Dec. 2010, to truncate the impulse response of the prototype filter used by the transmitter. Fig. 3 represents the impulse response of the truncated prototype filter to reduce the time spread of the FBMC symbols. This truncation is obtained by temporal windowing, 300, centered on the maximum of the impulse response. However, if this truncation actually makes it possible to reduce the latency time (in the first situation mentioned above) or to increase the transmission rate (in the second situation mentioned above), it degrades the spectral properties of the signal. , the gain in temporal location obtained by temporal windowing resulting in a loss in frequency localization. More precisely, the multiplication of the signal by a time window results in a convolution with a cardinal sinus in the frequency domain and therefore the appearance of secondary lobes in the transmission spectrum. The out-of-band rejection rate is therefore degraded.
    [0006] The object of the present invention is therefore to reduce the latency of FBMC communication and more generally to enable faster decoding of an FBMC symbol packet, without introducing out-of-band rejection level degradation.
    [0007] SUMMARY OF THE INVENTION The present invention is defined by a receiver FBMC for receiving at least one FBMC symbol packet, the FBMC symbols being transmitted by means of a plurality N of sub-channels and succeeding a frequency f = 1 / T with an overlap factor K, the receiver comprising a sampler for sampling at the frequency Nf the received baseband signal, a serial-to-parallel converter for forming successive sample blocks of size KN, an FFT module to perform an FFT of size KN on each of said blocks, a battery of analysis filters for performing spectral filtering and despreading on the frequency components at the output of the FFT module 5, said receiver further comprising a first multiplexer for stuffing with null values a first plurality (Mi) of the last samples of the last block of the FBMC packet at the input of the FFT module, without waiting for the end of r FBMC receipt of package. According to an advantageous exemplary embodiment, the overlap factor is equal to 4 and said first plurality of samples is equal to KN / 3 to within 10%. The receiver may further include a second multiplexer at the input of the FFT module for stuffing with nulls a second plurality of the first samples of the first block of the FBMC packet. In this case, if the overlap factor is 4, the second plurality of samples may also be equal to KN / 3 to within 10%. The invention also relates to a method for receiving at least one FBMC symbol packet, the FBMC symbols being transmitted by means of a plurality N of subchannels and succeeding each other at a frequency f = 1 / T with a factor of overlap K, said method comprising sampling at the frequency Nf of the received baseband signal, a series-to-parallel conversion to form successive sample blocks of size KN, a FFT of size KN on each of said blocks thus obtained, spectral filtering and despreading, in the frequency domain, of the frequency components at the output of the FFT. This reception method is advantageous in that it comprises, prior to the FFT, a first stuffing step with zero values of a first plurality (Mi) of the last samples of the last block of the FBMC packet, the step of padding being performed without waiting for the end of reception of the FBMC packet. According to an advantageous exemplary embodiment, the overlap factor is equal to 4 and said first plurality of samples is equal to KN / 3 to within 10%.
    [0008] The receiving method may further comprise, prior to the FFT, a second stuffing step by zero values of a second plurality of the first samples of the first block of the FBMC packet. In this case, if the overlap factor is equal to 4, the second plurality of samples can be advantageously chosen equal to KN / 3 to 10%.
    [0009] The reception method may further implement an equalization of the frequency components prior to the filtering and spectral despreading step. Finally, said reception method may comprise a demodulation step 0QAM after the spectral filtering and despreading step.
    [0010] BRIEF DESCRIPTION OF THE DRAWINGS Other features and advantages of the invention will become apparent upon reading preferred embodiments of the accompanying figures in which: FIG. 1 schematically shows a communication between a transmitter and a FBMC receiver using a handshake protocol; Fig. 2 represents two timing diagrams of FBMC packet transmission in TDMA mode; Fig. 3 represents the impulse response of a temporally truncated prototype filter; Fig. 4 schematically shows the architecture of a FBMC receiver according to a first embodiment of the invention; Fig. 5 shows the principle of zerosing the samples of the last FBMC symbol of a packet received by the receiver of FIG. 4; FIG. 6 shows the evolution of the signal-to-interference ratio at the receiver as a function of the stuffing rate by zeros; Figs.
    [0011] 7A and 7B show the variation of the saturated mode rate versus the number of users for two different packet sizes; Fig. 8 schematically shows the architecture of a FBMC receiver according to a second embodiment of the invention.
    [0012] DETAILED DESCRIPTION OF PARTICULAR EMBODIMENTS The idea underlying the present invention is not to window the FBMC signal at the transmitter and in particular not to truncate the impulse response of the prototype filter but on the contrary perform a processing at the receiver by stuffing the last samples of the last received block with zeros before performing the FFT. It has indeed been possible to show that it was possible to use only partial information to decode the last FBMC symbols.
    [0013] FIG. 4 schematically shows the structure of a FBMC receiver according to a first embodiment of the invention. The received FBMC signal, after being demodulated in baseband, is sampled by a sampler, 400, at the frequency Nf where f = 1/7; is the symbol frequency. The successive samples are grouped by a serial / parallel converter 410 as blocks of length KN where K is the overlap factor. A sliding FFT (the window of the sliding FFT of KT between two FFT calculations) is performed by means of an FFT module, 420, of KN consecutive samples. A multiplexer, 415, at the input of the FFT module, replaces the last M samples of the block corresponding to the last FBMC symbol of the packet with zeros. This multiplexer is controlled by an LPS control signal, for example from a counter (not shown) indicating the last FBMC symbol of the packet. Thus, it is understood that the receiver does not have to wait for the last M samples of the last block of the packet to perform the last FFT operation. The frequency components at the output of the FFT are then subjected, if appropriate, to an equalization in the frequency domain, in the equalizer 430. The equalizer is however an optional element of the invention, depending on the transfer function the transmission channel. After possible equalization, the outputs of the FFT are filtered and despread spectrally by the battery of analysis filters, 440. More precisely if dk are the 3034936 8 samples corresponding to 2K-1 frequencies (i -1) K +1 ,. .., iK, ..., (i + 1) K-1 of the FFT (i.e. the frequencies of the ith subchannel), the filter bank provides (for this ith subchannel) the sample: K-1 Gkdi, k k-K + 1 where the coefficients Gk are the values of the transfer function of the analysis filter (translated at the frequency <of the transfer function of the prototype filter). The data d thus obtained can undergo a plurality of operations, inverse of those implemented in the FBMC transmitter. For example, if the data has been subjected to a QAM (QAM Offset) modulation at the transmitter, then the data is subjected to 0QAM demodulation in a manner known per se. Similarly, if the data has been coded by channel coding and modulated by means of Q-area symbol modulation according to a Modulation and Coding Scheme (MCS) at the transmitter, the reverse operations are performed. at the receiver. Fig. 5 illustrates the principle of processing the last block of samples obtained from the FBMC package. The row of the sample for KN consecutive samples at the input of the FFT and the ordinate the amplitude are represented on the abscissa. The waveform 510 is that of a FBMC signal corresponding to a single subchannel and therefore corresponds to the impulse response of the prototype filter. It can be seen that the last input block of the FFT module consists of KN-I14, signal samples, 520, and M, stuffing samples consisting of null values, 530. Thus, the receiver does not have to wait for the end of the time stretching of the last FBMC symbol to complete the decoding of the packet. In other words, the last one or the last FBMC symbols (to take into account the overlap of these symbols) are decoded on the basis of partial information. It has been shown that this zeroing of the end of the last block of samples has little effect on the decoding performance of this block. Fig. 6 represents the evolution of the signal-to-interference ratio as a function of the jamming rate of the last block by zeros. More specifically, the ratio IV / NK is referred to as the stuffing ratio. Here we have K = 4 and N = 1024. It can be seen that the signal to interference ratio remains constant as long as the stuffing rate remains below 0.15 and then decreases to observe a plateau until a stuffing rate of about 1/3, then decreases again. Depending on the desired minimum SIR level, that is, the maximum acceptable bit error rate (BER), this curve can be used to determine the maximum stuffing rate. For example, in the case illustrated, if it is desired to have a signal-to-interference ratio greater than 45 dB, a stuffing rate of close to 0.3 will be chosen. It is thus understood that one gains approximately a time of T / 3 compared to a conventional FBMC demodulation while keeping a very good rate of out-of-band rejection since the FBMC signal emitted is unchanged. In general, for an overlap factor K = 4, the padding rate with zeros of the last block is chosen equal to KN / 3. FIGS.
    [0014] 7A and 7B represent the saturated mode rate of a FBMC communication system as a function of the number of users. Two protocols with handshakes have been considered here. The first protocol is a basic version of access sharing to the CSMA / CA resource (Carrier Sense Multiple Access with Collision Avoidance) implementing two handshakes and the second protocol is an evolved version, using two additional signaling signals. RTS / CTS (Request To Send / Clear To Send) and implementing four handshakes between the transmitter and the receiver. For each of these two protocols, the performance of a FBMC reception with a zero padding as described above has also been represented. For these two protocols, an MCS scheme with R = 3/4 efficiency channel coding and 16 QAM modulation was used.
    [0015] Fig.
    [0016] 7A corresponds to a packet size of 1500 bytes and FIG.
    [0017] 7B at a size 3034936 10 of 500 bytes packet. Note that at saturation, the bit rate gain is close to 10% for a packet size of 1500 bytes and close to 16% for a packet size of 500 bytes. As expected, the gain is all the more important as the packet size is small.
    [0018] Fig. 8 schematically shows the structure of a FBMC receiver according to a second embodiment of the invention. Unlike the first embodiment, zero padding occurs here both at the beginning of the first block of samples and at the end of the last block of samples of the FBMC packet. As in FIG. 4, the received FBMC signal is demodulated in baseband and then sampled at the frequency Nf. . The successive samples are grouped, serial / parallel converter, 810, as blocks of length KN where K is the overlap factor.
    [0019] The FFT 820 module performs a sliding FFT on a block of consecutive KN samples. A second multiplexer, 815, at the input of the FFT module, 820, replaces the last M samples of the block corresponding to the last FBMC symbol of the packet by zeros. Similarly, a second multiplexer, 813, at the input of the FFT module 820, replaces the M first samples of the block corresponding to the first FBMC symbol of the packet with zeros. According to one variant, the number of samples set to zero may be different for the first and second multiplexers. The first multiplexer is controlled by an initialization signal, IN), indicating the beginning of a new packet. The second multiplexer is controlled by a LPS control signal from a counter indicating the last FBMC symbol of the packet as in the first embodiment. Thus, the receiver does not take into account the time spread of the first symbol and the last symbol of the FBMC packet to decode it. It is then possible to reduce the size of the transmission intervals as in the timing diagram (b) of FIG. 2 without degrading the interference level and therefore without increasing the error rate.
    [0020] As in the first embodiment, the frequency components at the output of the FFT are subjected to an eventual equalization in the frequency domain by the equalizer 830, then to filtering and spectral despreading by the battery of analysis filters. , 840.
    [0021] As in the first embodiment, also, the output data of the filter bank 840 can then be demodulated as 0QAM, bit symbol demodulation followed by channel decoding. function of the operations performed on the transmitter side.
    权利要求:
    Claims (10)
    [0001]
    REVENDICATIONS1. A receiver FBMC for receiving at least one FBMC symbol packet, the FBMC symbols being transmitted by means of a plurality N of sub-channels and succeeding a frequency f = 1 / T with an overlap factor K, the receiver comprising a sampler (400,800) for sampling at the frequency Nf the received baseband signal, a serial to parallel converter (410, 810) for forming successive sample blocks of size KN, an FFT module (430, 830) for performing a FFT of size KN on each of said blocks, a battery of analysis filters (440, 840) for performing filtering and spectral despreading on the frequency components at the output of the FFT module, characterized in that it further comprises a first multiplexer (415, 815) for stuffing with zero values a first plurality (Mi) of the last samples of the last block of the FBMC packet at the input of the FFT module, without waiting for the end of reception of the packet F BMC.
    [0002]
    2. FBMC receiver according to claim 1, characterized in that the overlap factor is equal to 4 and said first plurality of samples is equal to KN / 3 to 10%.
    [0003]
    3. FBMC receiver according to claim 1 or 2, characterized in that it comprises a second multiplexer (813) at the input of the FFT module (820) for stuffing with zero values a second plurality of the first samples of the first block of the FBMC package.
    [0004]
    4. FBMC receiver according to one of the preceding claims, characterized in that the overlap factor is equal to 4 and the second plurality of samples is equal to KN / 3 to 10%. 25 3034936 13
    [0005]
    5. Method of receiving at least one FBMC symbol packet, the FBMC symbols being transmitted by means of a plurality N of subchannels and succeeding a frequency f = 1 / T with an overlap factor K, said method comprising sampling at the frequency Nf of the received baseband signal, serial-to-parallel conversion to form successive block sizes of KN size, FFT of size KN on each of said blocks thus obtained, filtering and despreading spectral, in the frequency domain, frequency components at the output of the FFT, characterized in that it comprises, prior to the FFT, a first stuffing step by zero values of a first plurality (Mi) of the last samples of the 10 last block of the FBMC packet, the stuffing step being performed without waiting for the end of reception of the FBMC packet.
    [0006]
    6. The reception method according to claim 5, characterized in that the overlap factor is 4 and said first plurality of samples is KNI3 to within 10%.
    [0007]
    7. Receiving method according to claim 5, characterized in that it further comprises, prior to the FFT, a second stuffing step by zero values of a second plurality of the first samples of the first block of the FBMC packet. 20
    [0008]
    8. receiving method according to claim 7, characterized in that the overlap factor is equal to 4 and the second plurality of samples is equal to KNI3 to 10%.
    [0009]
    9. Receiving method according to one of claims 5-8, characterized in that it comprises an equalization of the frequency components prior to the spectral filtering and despreading step. 3034936 14
    [0010]
    10. Receiving method according to one of claims 5-9, characterized in that it comprises a demodulation 0QAM after the spectral filtering and despreading step. 5
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    法律状态:
    2016-04-28| PLFP| Fee payment|Year of fee payment: 2 |
    2016-10-14| PLSC| Publication of the preliminary search report|Effective date: 20161014 |
    2017-04-28| PLFP| Fee payment|Year of fee payment: 3 |
    2018-04-26| PLFP| Fee payment|Year of fee payment: 4 |
    2020-01-10| ST| Notification of lapse|Effective date: 20191206 |
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